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PDF MC33077 Data sheet ( Hoja de datos )

Número de pieza MC33077
Descripción LOW NOISE OPERATIONAL AMPLIFIER
Fabricantes Motorola Semiconductors 
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Order this document by MC33077/D
Dual, Low Noise
Operational Amplifier
MC33077
The MC33077 is a precision high quality, high frequency, low noise
monolithic dual operational amplifier employing innovative bipolar design
techniques. Precision matching coupled with a unique analog resistor trim
technique is used to obtain low input offset voltages. Dual–doublet frequency
compensation techniques are used to enhance the gain bandwidth product
of the amplifier. In addition, the MC33077 offers low input noise voltage, low
temperature coefficient of input offset voltage, high slew rate, high AC and
DC open loop voltage gain and low supply current drain. The all NPN
transistor output stage exhibits no deadband cross–over distortion, large
output voltage swing, excellent phase and gain margins, low open loop
output impedance and symmetrical source and sink AC frequency
performance.
The MC33077 is tested over the automotive temperature range and is
available in plastic DIP and SO–8 packages (P and D suffixes).
Low Voltage Noise: 4.4 nV/ ǸHz @ 1.0 kHz
Low Input Offset Voltage: 0.2 mV
Low TC of Input Offset Voltage: 2.0 µV/°C
High Gain Bandwidth Product: 37 MHz @ 100 kHz
High AC Voltage Gain: 370 @ 100 kHz
High AC Voltage Gain: 1850 @ 20 kHz
Unity Gain Stable: with Capacitance Loads to 500 pF
High Slew Rate: 11 V/µs
Low Total Harmonic Distortion: 0.007%
Large Output Voltage Swing: +14 V to –14.7 V
www.DataSheet4U.com
High DC Open Loop Voltage Gain: 400 k (112 dB)
High Common Mode Rejection: 107 dB
Low Power Supply Drain Current: 3.5 mA
Dual Supply Operation: ±2.5 V to ±18 V
Representative Schematic Diagram (Each Amplifier)
DUAL, LOW NOISE
OPERATIONAL AMPLIFIER
SEMICONDUCTOR
TECHNICAL DATA
8
1
P SUFFIX
PLASTIC PACKAGE
CASE 626
8
1
D SUFFIX
PLASTIC PACKAGE
CASE 751
(SO–8)
PIN CONNECTIONS
R1 R6
R8 R11
R16 VCC
Q1 Q8
C1
R3
C3
J1 Q6
D3
Q11
R9
Z1
Q13
Q14
D4
Q17
Q19
D6 Q21
R13
Neg Q7 Q9
Q2
Q4 R5 C2
D1
Pos
Q10 Q12
C6
Q16
R14
R17 R18 Vout
D7 R19
C7
Q22
C8
Q1
Q5 R4
R7
R2
D2
R10 R12
D5
R15
Q20 R20
VEE
MOTOROLA ANALOG IC DEVICE DATA
Output 1 1
Inputs 1
2
3
VEE 4
8 VCC
1 7 Output 2
+
–6
2
+5
Inputs 2
(Dual, Top View)
ORDERING INFORMATION
Device
Operating
Temperature Range
Package
MC33077D
TA = – 40° to +85°C
MC33077P
SO–8
Plastic DIP
© Motorola, Inc. 1996
Rev 0
1

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MC33077 pdf
MC33077
Figure 9. Supply Current
versus Temperature
5.0
4.0
±15 V
3.0 ±5.0 V
2.0
1.0
0
–55 –25
VCM = 0 V
RL =
VO = 0 V
0 25 50 75
TA, AMBIENT TEMPERATURE (°C)
100
125
Figure 10. Common Mode Rejection
versus Frequency
120
100
VCM
ADM
+
VO
80
60
40
VCC = +15 V
VEE = –15 V
VCM = 0 V
20 VCM = ±1.5 V
TA = 25°C
0
100 1.0 k
CMR = 20Log
VCM
VO
× ADM
10 k 100 k
f, FREQUENCY (Hz)
1.0 M
10 M
Figure 11. Power Supply Rejection
versus Frequency
120 +PSR = 20Log VO/ADM
100 VCC
–PSR = 20Log VO/ADM
VEE
80 +PSR
–PSR
60
40
VCC = +15 V
20 VEE = –15 V
TA = 25°C
0
100 1.0 k
VCC
ADM
+
VEE
VO
10 k 100 k
f, FREQUENCY (Hz)
1.0 M
Figure 12. Gain Bandwidth Product
versus Supply Voltage
48
RL = 10 k
44
CL = 0 pF
f = 100 kHz
TA = 25°C
40
36
32
28
24
0 5 10 15
VCC, |VEE|, SUPPLY VOLTAGE (V)
20
Figure 13. Gain Bandwidth Product
versus Temperature
50
VCC = +15 V
46 VEE = –15 V
f = 100 kHz
42
RL = 10 k
CL = 0 pF
38
34
30
26
–55 –25 0 25 50 75 100 125
TA, AMBIENT TEMPERATURE (°C)
Figure 14. Maximum Output Voltage
versus Supply Voltage
20
TA = 25°C
15
RL = 10 k
10 Vp + RL = 2.0 k
5.0
0
–5.0
–10
–15
–20
0
Vp –
RL = 2.0 k
RL = 10 k
5.0 10 15
VCC, |VEE|, SUPPLY VOLTAGE (V)
20
MOTOROLA ANALOG IC DEVICE DATA
5

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MC33077 arduino
MC33077
occur, the amplifier’s phase will degrade severely causing the
amplifier to become unstable. Effective source resistances,
acting in conjunction with the input capacitance of the
amplifier, should be kept to a minimum to avoid creating such
a pole at the input (see Figure 31). There is minimal effect on
stability where the created input pole is much greater than the
closed loop corner frequency. Where amplifier stability is
affected as a result of a negative feedback resistor in
conjunction with the amplifier’s input capacitance, creating a
pole near the closed loop corner frequency, lead capacitor
compensation techniques (lead capacitor in parallel with the
feedback resistor) can be employed to improve stability. The
feedback resistor and lead capacitor RC time constant
should be larger than that of the uncompensated input pole
frequency. Having a high resistance connected to the
noninverting input of the amplifier can create a like instability
problem. Compensation for this condition can be
accomplished by adding a lead capacitor in parallel with the
noninverting input resistor of such a value as to make the RC
time constant larger than the RC time constant of the
uncompensated input resistor acting in conjunction with the
amplifiers input capacitance.
For optimum frequency performance and stability, careful
component placement and printed circuit board layout should
be exercised. For example, long unshielded input or output
leads may result in unwanted input output coupling. In order
to reduce the input capacitance, the body of resistors
connected to the input pins should be physically close to the
input pins. This not only minimizes the input pole creation for
optimum frequency response, but also minimizes extraneous
signal “pickup” at this node. Power supplies should be
decoupled with adequate capacitance as close as possible to
the device supply pin.
In addition to amplifier stability considerations, input
source resistance values should be low to take full advantage
of the low noise characteristics of the amplifier. Thermal
noise (Johnson Noise) of a resistor is generated by
thermally–charged carriers randomly moving within the
resistor creating a voltage. The rms thermal noise voltage in
a resistor can be calculated from:
Enr = / 4k TR × BW
where:
k = Boltzmann’s Constant (1.38 × 10–23 joules/k)
T = Kelvin temperature
R = Resistance in ohms
BW = Upper and lower frequency limit in Hertz.
By way of reference, a 1.0 kresistor at 25°C will produce
a 4.0 nV/Hz of rms noise voltage. If this resistor is
connected to the input of the amplifier, the noise voltage will
be gained–up in accordance to the amplifier’s gain
configuration. For this reason, the selection of input source
resistance for low noise circuit applications warrants serious
consideration. The total noise of the amplifier, as referred to
its inputs, is typically only 4.4 nV/Hz at 1.0 kHz.
The output of any one amplifier is current limited and thus
protected from a direct short to ground, However, under such
conditions, it is important not to allow the amplifier to exceed
the maximum junction temperature rating. Typically for ±15 V
supplies, any one output can be shorted continuously to
ground without exceeding the temperature rating.
0.1 µF
Figure 36. Voltage Noise Test Circuit
(0.1 Hz to 10 Hzp–p)
10 100 k
D.U.T.
+
2.0 k
4.7 µF
Voltage Gain = 50,000
24.3 k
+
1/2
MC33077
100 k
0.1 µF
4.3 k
2.2 µF
22 µF
Scope
×1
Rin = 1.0 M
110 k
Note: All capacitors are non–polarized.
MOTOROLA ANALOG IC DEVICE DATA
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