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PDF MC33035 Data sheet ( Hoja de datos )
| Número de pieza | MC33035 | |
| Descripción | BRUSHLESS DC MOTOR CONTROLLER | |
| Fabricantes | ON Semiconductor | |
| Logotipo |  |
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MC33035, NCV33035
Brushless DC
Motor Controller
The MC33035 is a high performance second generation monolithic
brushless DC motor controller containing all of the active functions
required to implement a full featured open loop, three or four phase
motor control system. This device consists of a rotor position decoder
for proper commutation sequencing, temperature compensated
reference capable of supplying sensor power, frequency
programmable sawtooth oscillator, three open collector top drivers,
and three high current totem pole bottom drivers ideally suited for
driving power MOSFETs.
Also included are protective features consisting of undervoltage
lockout, cycle−by−cycle current limiting with a selectable time
delayed latched shutdown mode, internal thermal shutdown, and a
unique fault output that can be interfaced into microprocessor
controlled systems.
Typical motor control functions include open loop speed, forward or
reverse direction, run enable, and dynamic braking. The MC33035 is
designed to operate with electrical sensor phasings of 60°/300° or
120°/240°, and can also efficiently control brush DC motors.
Features
• 10 to 30 V Operation
• Undervoltage Lockout
• 6.25 V Reference Capable of Supplying Sensor Power
• Fully Accessible Error Amplifier for Closed Loop Servo
Applications
• High Current Drivers Can Control External 3−Phase MOSFET
Bridge
• Cycle−By−Cycle Current Limiting
• Pinned−Out Current Sense Reference
• Internal Thermal Shutdown
• Selectable 60°/300° or 120°/240° Sensor Phasings
• Can Efficiently Control Brush DC Motors with External MOSFET
H−Bridge
• NCV Prefix for Automotive and Other Applications Requiring Site
and Control Changes
• Pb−Free Packages are Available
http://onsemi.com
P SUFFIX
PLASTIC PACKAGE
CASE 724
24
1
DW SUFFIX
PLASTIC PACKAGE
CASE 751E
(SO−24L)
24
1
PIN CONNECTIONS
Top Drive
Output
BT 1
AT 2
Fwd/Rev 3
Sensor
Inputs
SA 4
SB 5
SC 6
Output Enable 7
Reference Output 8
Current Sense
Noninverting Input
9
Oscillator 10
Error Amp
Noninverting Input
Error Amp
Inverting Input
11
12
24 CT
23 Brake
22 60°/120° Select
21 AB
20 BB
19 CB
Bottom
Drive
Outputs
18 VC
17 VCC
16 Gnd
15
Current Sense
Inverting Input
14 Fault Output
13
Error Amp Out/
PWM Input
(Top View)
ORDERING INFORMATION
See detailed ordering and shipping information in the package
dimensions section on page 27 of this data sheet.
DEVICE MARKING INFORMATION
See general marking information in the device marking
section on page 27 of this data sheet.
© Semiconductor Components Industries, LLC, 2004
April, 2004 − Rev. 7
1
Publication Order Number:
MC33035/D
1 page  
MC33035, NCV33035
100 4.0
VCC = 20 V
VC = 20 V
TA = 25°C
VCC = 20 V
VC = 20 V
2.0
RT = 4.7 k
CT = 10 nF
10 0
CT = 100 nF
CT = 10 nF
CT = 1.0 nF
0
1.0 10 100 1000
RT, TIMING RESISTOR (kΩ)
Figure 1. Oscillator Frequency versus
Timing Resistor
− 2.0
− 4.0
− 55
− 25 0 25 50 75 100
TA, AMBIENT TEMPERATURE (°C)
Figure 2. Oscillator Frequency Change
versus Temperature
125
56 40
48 60
40
Phase
80
32 100
24
16
8.0
0
− 8.0
−16
− 24
1.0 k
VCC = 20 V
VC = 20 V
VO = 3.0 V
RL = 15 k
CL = 100 pF
TA = 25°C
10 k
Gain
100 k
1.0 M
f, FREQUENCY (Hz)
120
140
160
180
200
220
240
10 M
Figure 3. Error Amp Open Loop Gain and
Phase versus Frequency
0
Vref
− 0.8 Source Saturation
(Load to Ground)
−1.6
VCC = 20 V
VC = 20 V
TA = 25°C
1.6
0.8
Gnd
Sink Saturation
(Load to Vref)
0
0 1.0 2.0 3.0 4.0 5.0
IO, OUTPUT LOAD CURRENT (mA)
Figure 4. Error Amp Output Saturation
Voltage versus Load Current
AV = +1.0
3.05
No Load
TA = 25°C
3.0
2.95
1.0 µs/DIV
Figure 5. Error Amp Small−Signal
Transient Response
AV = +1.0
4.5
No Load
TA = 25°C
3.0
1.5
5.0 µs/DIV
Figure 6. Error Amp Large−Signal
Transient Response
http://onsemi.com
5
5 Page 
MC33035, NCV33035
V VV
VVV
X
1
0
1
11 1 0 00 0
(Note 11)
NOTES: 1. V = Any one of six valid sensor or drive combinations X = Don’t care.
2. The digital inputs (Pins 3, 4, 5, 6, 7, 22, 23) are all TTL compatible. The current sense input (Pin 9) has a 100 mV threshold with respect to Pin 15.
A logic 0 for this input is defined as < 85 mV, and a logic 1 is > 115 mV.
3. The fault and top drive outputs are open collector design and active in the low (0) state.
4. With 60°/120° select (Pin 22) in the high (1) state, configuration is for 60° sensor electrical phasing inputs. With Pin 22 in low (0) state, configuration
is for 120° sensor electrical phasing inputs.
5. Valid 60° or 120° sensor combinations for corresponding valid top and bottom drive outputs.
6. Invalid sensor inputs with brake = 0; All top and bottom drives off, Fault low.
7. Invalid sensor inputs with brake = 1; All top drives off, all bottom drives on, Fault low.
8. Valid 60° or 120° sensor inputs with brake = 1; All top drives off, all bottom drives on, Fault high.
9. Valid sensor inputs with brake = 1 and enable = 0; All top drives off, all bottom drives on, Fault low.
10. Valid sensor inputs with brake = 0 and enable = 0; All top and bottom drives off, Fault low.
11. All bottom drives off, Fault low.
Figure 20. Three Phase, Six Step Commutation Truth Table (Note 1)
Pulse Width Modulator
The use of pulse width modulation provides an energy
efficient method of controlling the motor speed by varying
the average voltage applied to each stator winding during the
commutation sequence. As CT discharges, the oscillator sets
both latches, allowing conduction of the top and bottom
drive outputs. The PWM comparator resets the upper latch,
terminating the bottom drive output conduction when the
positive−going ramp of CT becomes greater than the error
amplifier output. The pulse width modulator timing diagram
is shown in Figure 21. Pulse width modulation for speed
control appears only at the bottom drive outputs.
Current Limit
Continuous operation of a motor that is severely
over−loaded results in overheating and eventual failure.
This destructive condition can best be prevented with the use
of cycle−by−cycle current limiting. That is, each on−cycle
is treated as a separate event. Cycle−by−cycle current
limiting is accomplished by monitoring the stator current
build−up each time an output switch conducts, and upon
sensing an over current condition, immediately turning off
the switch and holding it off for the remaining duration of
oscillator ramp−up period. The stator current is converted to
a voltage by inserting a ground−referenced sense resistor RS
(Figure 36) in series with the three bottom switch transistors
(Q4, Q5, Q6). The voltage developed across the sense
resistor is monitored by the Current Sense Input (Pins 9 and
15), and compared to the internal 100 mV reference. The
current sense comparator inputs have an input common
mode range of approximately 3.0 V. If the 100 mV current
sense threshold is exceeded, the comparator resets the lower
sense latch and terminates output switch conduction. The
value for the current sense resistor is:
RS
+
0.1
Istator(max)
The Fault output activates during an over current condition.
The dual−latch PWM configuration ensures that only one
single output conduction pulse occurs during any given
oscillator cycle, whether terminated by the output of the
error amp or the current limit comparator.
http://onsemi.com
11
11 Page | ||
| Páginas | Total 28 Páginas | |
| PDF Descargar | [ Datasheet MC33035.PDF ] | |
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