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Número de pieza TDA9802
Descripción Multistandard VIF-PLL demodulator and FM-PLL detector
Fabricantes NXP Semiconductors 
Logotipo NXP Semiconductors Logotipo



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INTEGRATED CIRCUITS
DATA SHEET
TDA9802
Multistandard VIF-PLL
demodulator and FM-PLL detector
Preliminary specification
File under Integrated Circuits, IC02
November 1992

1 page




TDA9802 pdf
Philips Semiconductors
Multistandard VIF-PLL demodulator and
FM-PLL detector
Preliminary specification
TDA9802
FUNCTIONAL DESCRIPTION
Vision IF input
The vision IF amplifier consists of three AC-coupled
differential amplifier stages; each stage comprises a
controlled feedback network by means of emitter
degeneration.
IF and tuner AGC
The automatic control voltage to maintain the video output
signal at a constant level is generated according to the
transmission standard. For negative modulation the
peak-sync level is detected, for positive modulation the
peak white level is detected. The AGC detector charges
and discharges the capacitor on pin 19 to set the IF gain
and the tuner gain. The standard is switched by the voltage
on pin 8. To reduce the response time for positive
modulation (which needs a very long time constant) a
black level detector (CBL) increases the AGC capacitor
discharge current for low-level video signals.
The AGC capacitor voltage is transferred to an internal IF
control signal, and is fed to the tuner AGC to generate the
tuner AGC output current on pin 12 (open-collector
output). The tuner AGC voltage take over point is adjusted
on pin 3. This allows the tuner and the IF SAW filter to be
matched to achieve the optimum IF input level.
Frequency detector, phase detector and video
demodulator
The IF amplifier output signal is fed to a frequency detector
and to a phase detector. The frequency detector is
operational before lock-in. A DC current is generated
which is proportional to the frequency difference between
the input frequency and the VCO frequency. After lock-in,
the frequency detector and the phase detector generate a
DC current proportional to the phase difference between
VCO and input signals. The control signal for the VCO is
provided by the phase detector. The video demodulator is
a linear multiplier, designed for low distortion and wide
bandwidth. The vision IF input signal is multiplied by the
in-phase component of the VCO output. The demodulated
output signal is fed via an integrated low-pass filter
(fg = 12 MHz) to the video amplifier for suppression of the
carrier harmonics. The polarity of the video signal is
switched in the demodulator stage according to the TV
standard.
VCO and travelling wave divider
The VCO operates with a symmetrically-connected
reference LC-circuit, operating at double vision carrier
frequency. Frequency control is performed by an internal
varicap diode. The voltage to set the VCO frequency to the
actual frequency of double vision carrier frequency, is also
amplified and converted for the AFC output current.
The VCO signal is divided-by-two in a travelling wave
divider, which generates two differential output signals
with 90 degree phase difference independent of
frequency.
Video amplifier, buffer and noise clipping
The video amplifier is a wide bandwidth operational
amplifier with internal feedback. Dependent on
transmission standard, a level shifter provides the same
sync level for positive as for negative modulation. A
nominal positive modulated video signal of 1 V (p-p) is
present on the composite video output (pin 13).
The input impedance of the 7 dB wideband buffer amplifier
(with internal feedback) is suitable for ceramic sound trap
filters.
The CVBS output (pin 7) provides a positive video signal
of 2 V (p-p). Noise clipping is provided internally.
Sound demodulation
The FM sound intercarrier signal is fed to pin 11 and
through a limiter amplifier before it is demodulated. This
achieves high sensitivity and high AM suppression. The
limiter amplifier consists of seven internal AC-coupled
stages, minimizing the DC offset.
The FM-PLL demodulator consists of an RC-oscillator,
loop filter and phase detector. The oscillator frequency is
locked on the FM intercarrier signal from the limiter
amplifier.
As a result of this locking, the RC-oscillator is
frequency-modulated. The modulating signal voltage (AF
signal) is used to control the oscillator frequency. By this,
the FM-PLL operates as an FM demodulator.
The audio frequency amplifier with internal feedback is
designed for high gain and high common mode rejection.
The low-level AF signal output from the FM-PLL
demodulator is amplified and buffered in a low-ohmic
audio signal output stage (pin 9). An external decoupling
capacitor on pin 10 removes the DC voltage from the audio
amplifier input.
November 1992
5

5 Page





TDA9802 arduino
Philips Semiconductors
Multistandard VIF-PLL demodulator and
FM-PLL detector
Preliminary specification
TDA9802
SYMBOL
PARAMETER
CONDITIONS
MIN. TYP. MAX.
FMPLL sound demodulator and AF output (pin 9) see note 18
fi FM catching range of PLL
holding range of PLL
4
3.5
7
8
tacqu
fAF
acquisition time
frequency deviation
THD < 1.5%;
see note 19
− −4
− − ±50
V10 DC voltage at decoupling capacitor
voltage dependent on
VCO frequency;
see note 20
1.2
2.2
Vo AF
AF output signal (RMS value, pin 9)
fAF = ±27 kHz;
see Fig.11
280 350 420
maximum output signal handling
THD < 1.5%
0.8 − −
Vo temperature drift of AF output signal
R9 output resistance
T = 0 to+70 °C
0.2 0.5
100
RL load resistance (pin 9)
2.2 − −
V9 DC voltage
B 3 dB audio frequency bandwidth
1.6 2.0 2.4
95 120
THD
total harmonic distortion
0.1 0.5
S/N (W) signal-to-noise ratio, weighted
CCIR468-4; see Fig.11 50 55
VSC residual sound carrier and harmonics (RMS
value)
− − 75
αAM AM suppression
see Fig.10;
46
AM: f = 1 kHz; m = 0.3
50
RR ripple rejection on pin 9
see Fig.9
26 30
Measurements from IF input to audio output (pin 9)
S/N (W) weighted signal-to-noise ratio referred to
54% FM modulation
6 kHz sinusoidal waveform
black level
white picture
560 between pins 13 and 11
CCIR468-4; with offset alignment on pin 4
black-to-white
sync only
39 46
39 48
39 46
UNIT
MHz
MHz
µs
kHz
V
mV
V
dB
k
V
kHz
%
dB
mV
dB
dB
dB
dB
dB
November 1992
11

11 Page







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